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raccourcis clavier

Frequency Domain and a la carte.

Open-loop versus closed-loop

Transient and steady-state response

Stability

Total response = Natural response + Forced response
- Natural response (homogeneous solution): evolution of system due to initial conditions
- Forced response (particular solution): evolution of system due to input

Control objects:

Stabilize the system
Produce the desired transient response
Decrease/eliminate steady-state error
Make system “robust” to withstand disturbances and variations in parameters
Achieve optimal performance

Block diagrams representation of a system

stateDiagram-v2
  direction LR

  [*] --> System: r(t)
  System --> End: c(t)

System as linear differential equation

graph LR
    Diff{{differential equations}} -- "Laplace transform" --> Algebraic{{algebraic equations}} -- "inverse Laplace transform" --> End{{time domain solution}}

\mathcal{L} \{f(t)\} = \int_0^{\infty}f(t)^{-st}dt = F(s)

\begin{array}{c c c} \hline \text{Item no.} & f(t) & F(s) \\ \hline 1. & \delta(t) & 1 \\ 2. & u(t) & \frac{1}{s} \\ 3. & tu(t) & \frac{1}{s^2} \\ 4. & t^n u(t) & \frac{n!}{s^{n+1}} \\ 5. & e^{-at}u(t) & \frac{1}{s + a} \\ 6. & \sin(\omega t)u(t) & \frac{\omega}{s^2 + \omega^2} \\ 7. & \cos(\omega t)u(t) & \frac{s}{s^2 + \omega^2} \\ \hline \end{array}

\delta{(t)} = 0, \quad t \neq 0,\quad \int_0^{\infty}{\delta{(t)}}dt=1

example: Given a unit step function $u(t) = \begin{cases} 0 & t < 0 \\ 1 & t \ge 0 \end{cases}$

\begin{aligned} U(s) = \mathcal{L} \{u(t)\} &= \int_{0}^{\infty} u(t) e^{-st} dt = -\frac{1}{s} e^{-st} dt \\ U(s) &= -\frac{1}{s}(0-1) = \frac{1}{s} \end{aligned}

inverse form

\mathcal{L}^{-1} \{ F(s) \} = \frac{1}{2\pi j} \lim_{\omega \to \infty} \int_{\sigma-j\omega}^{\sigma+j\omega} F(s) e^{st} \, ds

Properties

\begin{aligned} & f(0-)\text{: initial condition just before 0} \\[12pt] & \textbf{Linearity:} \quad \mathcal{L}\{k_1 f_1(t) \pm k_2 f_2(t)\} = k_1 F_1(s) \pm k_2 F_2(s) \\[12pt] & \textbf{Differentiation:} \\ & \quad \mathcal{L}\left\{\frac{df(t)}{dt}\right\} = sF(s) - f(0^-) \\ & \quad \mathcal{L}\left\{\frac{d^2f(t)}{dt^2}\right\} = s^2 F(s) - sf(0^-) - f'(0^-) \\[12pt] & \textbf{Frequency Shifting:} \quad \mathcal{L}\{e^{-at}f(t)\} = F(s + a) \\ \end{aligned}

Transfer function

$n^{th}$ order linear, time-invariant (LTI) differential equation:

a_n \frac{d^n c(t)}{dt^n} + a_{n-1} \frac{d^{n-1} c(t)}{dt^{n-1}} + \cdots + a_0 c(t) = b_m \frac{d^m r(t)}{dt^m} + b_{m-1} \frac{d^{m-1} r(t)}{dt^{m-1}} + \cdots + b_0 r(t)

takes Laplace transform from both side

\begin{aligned} & a_n s^n C(s) + a_{n-1} s^{n-1} C(s) + \cdots + a_0 C(s) \text{ and init terms for } c(t) \\ & = b_m s^m R(s) + b_{m-1} s^{m-1} R(s) + \cdots + b_0 R(s) \text{ and init terms for } r(t) \\ \end{aligned}

assume initial conditions are zero

\begin{aligned} (a_n s^n + a_{n-1} s^{n-1} + \cdots + a_0)C(s) &= (b_m s^m + b_{m-1} s^{m-1} + \cdots + b_0)R(s) \\[8pt] \frac{C(s)}{R(s)} &= G(s) = \frac{b_m s^m + b_{m-1} s^{m-1} + \cdots + b_0}{a_n s^n + a_{n-1} s^{n-1} + \cdots + a_0} \end{aligned}

Transfer function

$G(s)=\frac{C(s)}{R(s)}$

Q: $G(s) = \frac{1}{S+2}$ . Input: $u(t)$ . What is $y(t)$ ?

\begin{aligned} Y(s) &= G(s)\cdot u(s) \rightarrow Y(s)=\frac{1}{s(s+2)} = \frac{A}{s} + \frac{B}{s+2} = \frac{1}{2\cdot{s}} - \frac{1}{2\cdot{(s+2)}} \\ y(t) &= -\frac{1}{2}(1-e^{-2t})u(t) \end{aligned}

Partial fraction expansion

\begin{aligned} F(s) &= \frac{N(s)}{D(s)} \\[8pt] N(s) &: m^{th} \text{ order polynomial in } s \\ D(s) &: n^{th} \text{ order polynomial in } s \\ \end{aligned}

Decomposition of $\frac{N(s)}{D(s)}$

Divide if improper: $\frac{N(s)}{D(s)}$ such that $\text{degree of }N(s) \leq \text{degree of } D(s)$ such that $\frac{N(s)}{D(s)} = \text{a polynomial } + \frac{N_1(s)}{D(s)}$
Factor Denominator: into factor form $(ps+q)^m \text{ and } (as^2+bs+c)^n$
Linear Factors: $(ps+q)^m$ such that: $\sum_{j=1}^{m}\frac{A_j}{(ps+q)^j}$
Quadratic Factors: $(as^2+bs+c)^n$ such that $\sum_{j=1}^{n}{\frac{B_j s+C_j}{(as^2+bs+c)^j}}$
Determine Unknown

Stability analysis using Root of $D(s)$

roots of $D(s)$

roots of $D(s)$ as poles

G(s) = \frac{N(s)}{D(s)} = \frac{N(s)}{\prod_{j=1}^{n}(s+p_j)} = \sum_{j=1}^{n}{\frac{A_j}{s+p_j}}

$p_i$ can be imaginary

Solving for $g(t)$ gives

g(t) = \sum_{j=1}^{n}{\mathcal{L}^{-1}\{\frac{A_j}{(s+p_j)}\}} = \sum_{j=1}^{n}{A_je^{-p_jt}}

stability analysis

Important

If $\sigma_i > 0$ then pole is in the left side of imaginary plane, and system is stable

Complex root

For poles at $s=\sigma_i \pm j\omega$ we get

\frac{\alpha + j\beta}{s + \sigma_i + j\omega_i} + \frac{\alpha - j\beta}{s + \sigma_i - j\omega_i}

Wants to be on LHP for time-function associated with $s$ plane to be stable

Impedance of Inductor

Z(s) = \frac{V(s)}{I(s)} = Ls

since the voltage-current relation for an inductor is $v(t) = L\frac{di(t)}{dt}$

Impedance of Capacitor

Z(s) = \frac{V(s)}{I(s)} = \frac{1}{Cs}

since the voltage-current relation for a capacitor is $v(t) = \frac{1}{C} \int_0^{t}{i(\tau) d\tau}$

Open-loop versus closed-loop

Transient and steady-state response

Stability

Total response = Natural response + Forced response
- Natural response (homogeneous solution): evolution of system due to initial conditions
- Forced response (particular solution): evolution of system due to input

Control objects:

Stabilize the system
Produce the desired transient response
Decrease/eliminate steady-state error
Make system “robust” to withstand disturbances and variations in parameters
Achieve optimal performance

Block diagrams representation of a system

stateDiagram-v2
  direction LR

  [*] --> System: r(t)
  System --> End: c(t)

System as linear differential equation

url: thoughts/Laplace-transform
Laplace transform
graph LR
    Diff{{differential equations}} -- "Laplace transform" --> Algebraic{{algebraic equations}} -- "inverse Laplace transform" --> End{{time domain solution}}
$\mathcal{L} \{f(t)\} = \int_0^{\infty}f(t)^{-st}dt = F(s)$ $\begin{array}{c c c} \hline \text{Item no.} & f(t) & F(s) \\ \hline 1. & \delta(t) & 1 \\ 2. & u(t) & \frac{1}{s} \\ 3. & tu(t) & \frac{1}{s^2} \\ 4. & t^n u(t) & \frac{n!}{s^{n+1}} \\ 5. & e^{-at}u(t) & \frac{1}{s + a} \\ 6. & \sin(\omega t)u(t) & \frac{\omega}{s^2 + \omega^2} \\ 7. & \cos(\omega t)u(t) & \frac{s}{s^2 + \omega^2} \\ \hline \end{array}$ $\delta{(t)} = 0, \quad t \neq 0,\quad \int_0^{\infty}{\delta{(t)}}dt=1$
example: Given a unit step function $u(t) = \begin{cases} 0 & t < 0 \\ 1 & t \ge 0 \end{cases}$
$\begin{aligned} U(s) = \mathcal{L} \{u(t)\} &= \int_{0}^{\infty} u(t) e^{-st} dt = -\frac{1}{s} e^{-st} dt \\ U(s) &= -\frac{1}{s}(0-1) = \frac{1}{s} \end{aligned}$
inverse form
$\mathcal{L}^{-1} \{ F(s) \} = \frac{1}{2\pi j} \lim_{\omega \to \infty} \int_{\sigma-j\omega}^{\sigma+j\omega} F(s) e^{st} \, ds$ Lien vers l'original

Properties

\begin{aligned} & f(0-)\text{: initial condition just before 0} \\[12pt] & \textbf{Linearity:} \quad \mathcal{L}\{k_1 f_1(t) \pm k_2 f_2(t)\} = k_1 F_1(s) \pm k_2 F_2(s) \\[12pt] & \textbf{Differentiation:} \\ & \quad \mathcal{L}\left\{\frac{df(t)}{dt}\right\} = sF(s) - f(0^-) \\ & \quad \mathcal{L}\left\{\frac{d^2f(t)}{dt^2}\right\} = s^2 F(s) - sf(0^-) - f'(0^-) \\[12pt] & \textbf{Frequency Shifting:} \quad \mathcal{L}\{e^{-at}f(t)\} = F(s + a) \\ \end{aligned}

Transfer function

$n^{th}$ order linear, time-invariant (LTI) differential equation:

a_n \frac{d^n c(t)}{dt^n} + a_{n-1} \frac{d^{n-1} c(t)}{dt^{n-1}} + \cdots + a_0 c(t) = b_m \frac{d^m r(t)}{dt^m} + b_{m-1} \frac{d^{m-1} r(t)}{dt^{m-1}} + \cdots + b_0 r(t)

takes Laplace transform from both side

\begin{aligned} & a_n s^n C(s) + a_{n-1} s^{n-1} C(s) + \cdots + a_0 C(s) \text{ and init terms for } c(t) \\ & = b_m s^m R(s) + b_{m-1} s^{m-1} R(s) + \cdots + b_0 R(s) \text{ and init terms for } r(t) \\ \end{aligned}

assume initial conditions are zero

\begin{aligned} (a_n s^n + a_{n-1} s^{n-1} + \cdots + a_0)C(s) &= (b_m s^m + b_{m-1} s^{m-1} + \cdots + b_0)R(s) \\[8pt] \frac{C(s)}{R(s)} &= G(s) = \frac{b_m s^m + b_{m-1} s^{m-1} + \cdots + b_0}{a_n s^n + a_{n-1} s^{n-1} + \cdots + a_0} \end{aligned}

Transfer function

$G(s)=\frac{C(s)}{R(s)}$

Q: $G(s) = \frac{1}{S+2}$ . Input: $u(t)$ . What is $y(t)$ ?

\begin{aligned} Y(s) &= G(s)\cdot u(s) \rightarrow Y(s)=\frac{1}{s(s+2)} = \frac{A}{s} + \frac{B}{s+2} = \frac{1}{2\cdot{s}} - \frac{1}{2\cdot{(s+2)}} \\ y(t) &= -\frac{1}{2}(1-e^{-2t})u(t) \end{aligned}

Partial fraction expansion

\begin{aligned} F(s) &= \frac{N(s)}{D(s)} \\[8pt] N(s) &: m^{th} \text{ order polynomial in } s \\ D(s) &: n^{th} \text{ order polynomial in } s \\ \end{aligned}

Decomposition of $\frac{N(s)}{D(s)}$

Divide if improper: $\frac{N(s)}{D(s)}$ such that $\text{degree of }N(s) \leq \text{degree of } D(s)$ such that $\frac{N(s)}{D(s)} = \text{a polynomial } + \frac{N_1(s)}{D(s)}$
Factor Denominator: into factor form $(ps+q)^m \text{ and } (as^2+bs+c)^n$
Linear Factors: $(ps+q)^m$ such that: $\sum_{j=1}^{m}\frac{A_j}{(ps+q)^j}$
Quadratic Factors: $(as^2+bs+c)^n$ such that $\sum_{j=1}^{n}{\frac{B_j s+C_j}{(as^2+bs+c)^j}}$
Determine Unknown

Stability analysis using Root of $D(s)$

roots of $D(s)$

roots of $D(s)$ as poles

G(s) = \frac{N(s)}{D(s)} = \frac{N(s)}{\prod_{j=1}^{n}(s+p_j)} = \sum_{j=1}^{n}{\frac{A_j}{s+p_j}}

$p_i$ can be imaginary

Solving for $g(t)$ gives

g(t) = \sum_{j=1}^{n}{\mathcal{L}^{-1}\{\frac{A_j}{(s+p_j)}\}} = \sum_{j=1}^{n}{A_je^{-p_jt}}

stability analysis

Important

If $\sigma_i > 0$ then pole is in the left side of imaginary plane, and system is stable

Complex root

For poles at $s=\sigma_i \pm j\omega$ we get

\frac{\alpha + j\beta}{s + \sigma_i + j\omega_i} + \frac{\alpha - j\beta}{s + \sigma_i - j\omega_i}

Wants to be on LHP for time-function associated with $s$ plane to be stable

Impedance of Inductor

Z(s) = \frac{V(s)}{I(s)} = Ls

since the voltage-current relation for an inductor is $v(t) = L\frac{di(t)}{dt}$

Impedance of Capacitor

Z(s) = \frac{V(s)}{I(s)} = \frac{1}{Cs}

since the voltage-current relation for a capacitor is $v(t) = \frac{1}{C} \int_0^{t}{i(\tau) d\tau}$

Frequency Domain and a la carte.

Étiquette

publié à

modifié à

durée

source

Block diagrams representation of a system

Laplace transform

inverse form

Properties

Transfer function

Partial fraction expansion

Decomposition of $\frac{N(s)}{D(s)}$

Stability analysis using Root of $D(s)$

stability analysis

Complex root

Impedance of Inductor

Impedance of Capacitor

Vous pourriez aimer ce qui suit

Liens retour

Frequency Domain and a la carte.

Étiquette

publié à

modifié à

durée

source

Block diagrams representation of a system

Laplace transform

inverse form

Properties

Transfer function

Partial fraction expansion

Decomposition of N(s)D(s)\frac{N(s)}{D(s)}D(s)N(s)​

Stability analysis using Root of D(s)D(s)D(s)

stability analysis

Complex root

Impedance of Inductor

Impedance of Capacitor

Vous pourriez aimer ce qui suit

Liens retour

Decomposition of $\frac{N(s)}{D(s)}$

Stability analysis using Root of $D(s)$